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HIP6017BCB

Advanced PWM and Dual Linear Power Control

Intersil 

HIP6017B

LUV

OC1

0.15V +

-

SS

+

4V -

OV

OVER

CURRENT

LATCH

SQ

INHIBIT

R

S

COUNTER

R

FAULT VCC

LATCH

UP

SQ

POR

R

FAULT

FIGURE 7. FAULT LOGIC - SIMPLIFIED SCHEMATIC

soft-start interval (T4 in Figure 6). At start-up, this allows

VOUT2 and VOUT3 to slew up without generating a fault.

Cycling the bias input voltage (+12VIN on the VCC pin) off

then on resets the counter and the fault latch.

Over-Voltage Protection

During operation, a short on the upper PWM MOSFET (Q1)

causes VOUT1 to increase. When the output exceeds the

over-voltage threshold of 115% (typical) of DACOUT, the

over-voltage comparator trips to set the fault latch and turns Q2

on as required in order to regulate VOUT1 to 1.15 x DACOUT.

This blows the input fuse and reduces VOUT1. The fault latch

raises the FAULT/RT pin close to VCC potential.

A separate over-voltage circuit provides protection during

the initial application of power. For voltages on the VCC pin

below the power-on reset (and above ~4V), VOUT1 is

monitored for voltages exceeding 1.26V. Should VSEN1

exceed this level, the lower MOSFET (Q2) is driven on as

needed to regulate VOUT1 to 1.26V.

Over-Current Protection

All outputs are protected against excessive over-currents.

The PWM controller uses the upper MOSFET’s on-

resistance, rDS(ON) to monitor the current for protection

against shorted outputs. The linear regulator monitors the

current of the integrated power device and signals an over-

current condition for currents in excess of 230mA.

Additionally, both the linear regulator and the linear controller

monitor FB2 and FB3 for under-voltage to protect against

excessive currents.

Figures 8 and 9 illustrate the over-current protection with

an overload on OUT1. The overload is applied at T0 and

the current increases through the output inductor (LOUT1).

At time T1, the OVER-CURRENT1 comparator trips when

the voltage across Q1 (ID x rDS(ON)) exceeds the level

programmed by ROCSET. This inhibits all outputs,

discharges the soft-start capacitor (CSS) with a 11mA

current sink, and increments the counter. CSS recharges at

T2 and initiates a soft-start cycle with the error amplifiers

clamped by soft-start. With OUT1 still overloaded, the

inductor current increases to trip the over-current

comparator. Again, this inhibits all outputs, but the soft-start

voltage continues increasing to 4V before discharging. The

counter increments to 2. The soft-start cycle repeats at T3

and trips the over-current comparator. The SS pin voltage

increases to 4V at T4 and the counter increments to 3. This

sets the fault latch to disable the converter. The fault is

reported on the FAULT/RT pin.

10V

0V

4V

2V

0V

COUNT

=1

FAULT

REPORTED

COUNT

=2

OVERLOAD

APPLIED

COUNT

=3

0A

T0 T1

T2

T3

T4

TIME

FIGURE 8. OVER-CURRENT OPERATION

The linear regulator operates in the same way as PWM1 to

over-current faults. Additionally, the linear regulator and

linear controller monitor the feedback pins for an under-

voltage. Should excessive currents cause FB2 or FB3 to fall

below the linear under-voltage threshold, the LUV signal

sets the over-current latch if CSS is fully charged. Blanking the

LUV signal during the CSS charge interval allows the linear

outputs to build above the under-voltage threshold during

normal start-up. Cycling the bias input power off then on

resets the counter and the fault latch.

Resistor ROCSET1 programs the over-current trip level for the

PWM converter. As shown in Figure 9, the internal 200µA

current sink develops a voltage across ROCSET (VSET) that is

referenced to VIN. The DRIVE signal enables the over-current

comparator (OVER-CURRENT1). When the voltage across

the upper MOSFET (VDS(ON)) exceeds VSET, the over-

current comparator trips to set the over-current latch. Both

VSET and VDS are referenced to VIN and a small capacitor

across ROCSET helps VOCSET track the variations of VIN due

to MOSFET switching. The over-current function will trip at a

peak inductor current (IPEAK) determined by:

IPEAK = I--O-----C----S----Er--D--T---S--×--(--OR----N-O---)--C----S----E----T-

The OC trip point varies with MOSFET’s temperature. To

avoid over-current tripping in the normal operating load

8

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